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TDA7360 22w bridge / stereo audio amplifier with clipping detector very few external components no boucherot cells no boostrap capacitors high output power no switch on/off noise very low stand-by current fixed gain (20db stereo) programmable turn-on delay clipping detector protections: output ac-dc short circuit to ground and to supply voltage very inductive loads loudspeaker protection overrating chip temperature load dump voltage fortuitous open ground esd description the TDA7360 is a new technology class ab audio power amplifier in the multiwatt ? package designed for car radio applications. thanks to the fully complementary pnp/npn out- put configuration the high power performance of the TDA7360 is obtained without bootstrap ca- pacitors. a delayed turn-on mute circuit eliminates audible on/off noise, and a novel short circuit protection system prevents spurious intervention with highly inductive loads. the device provides a circuit for the detection of clipping in the output stages. the output, an open collector, is able to drive systems with automatic volume control. this is advanced information on a new product now in development or undergoing evaluation. details are subject to change without notice. october 1998 ? application circuit (bridge) multiwatt11v multiwatt11h ordering numbers: TDA7360 TDA7360hs 1/22
pin connection (top view) absolute maximum ratings symbol parameter test conditions unit v s operating supply voltage 18 v v s dc supply voltage 28 v v s peak supply voltage (for t = 50ms) 50 v i o output peak current (non rep. for t = 100 m s) 5 a i o output peak current (rep. freq. > 10hz) 4 a p tot power dissipation at t case =85 c36w t stg , t j storage and junction temperature -40 to 150 c thermal data symbol description value unit r th j-case thermal resistance junction-case max 1.8 c/w TDA7360 2/22
electrical characteristics (refer to the test circuits, t amb =25 c, v s = 14.4v, f = 1khz unless otherwise specified) symbol parameter test condition min. typ. max. unit v s supply voltage range 8 18 v i d total quiescent drain current stereo configuration 120 ma a sb stand-by attenuation 60 80 db i sb stand-by current 100 m a i co clip detector average current pin 2 pull up to 5v d = 1% with 10k w d=5% 70 m a 130 m a stereo p o output power (each channel) d = 10% r l = 1.6 w r l =2 w r l = 3.2 w r l =4 w 7 12 11 8 6.5 w w w w d distortion p o = 0.1 to 4w r l = 3.2 w 0.05 0.5 % svr supply voltage rejection r g = 10k w c3 = 22 m f f = 100hz c3 = 100 m f 45 62 db db ct crosstalk f = 1khz f = 10khz 45 55 db db r i input resistance 50 k w g v voltage gain 20 db g v voltage gain match 1 db e in input noise voltage 22 hz to 22khz rg = 50 w r g = 10k w r g = 2.5 3 3.5 5 7 bridge v os output offset voltage 250 mv p o output power d = 10%; r l =4 w d = 10%; r l = 3.2 w 16 20 22 w w d distortion p o = 0.1 to 10w; r l = 3.2 w 0.05 1 % svr supply voltage rejection r g = 10k w c3 = 22 m f f = 100hz c3 = 100 m f 45 62 db db r i input resistance 50 k w g v voltage gain 26 db e in input noise voltage 22hz to 22khz r g =50 w r g = 10k w 3.5 4 m v m v m v m v TDA7360 3/22
figure 1: stereo test and appication circuit figure 2: p.c. board and component layout (stereo) of the circuit of fig. 1 (1:1 scale) 1000 m f 1000 m f TDA7360 4/22
figure 3: bridge test and appication circuit figure 4: p.c. board and layout (bridge) of the circuit of fig. 3 (1:1 scale) TDA7360 5/22
recommended values of the external components (ref to the stereo test and applica- tion circuit) component recommended value purpose larger than the recomm. value smaller than the recomm. value c1 0.22 m f input decoupling (ch1) ee c2 0.22 m f input decoupling (ch2) ee c3 100 m f s up ply v olta ge rejection filtering capacitor longer turn-on delay time - worse supply voltage rejection. - shorter turn-on delay time - danger of noise (pop) c4 22 m f stand-by on/off delay delayed turn-off by stand-by switch danger of noise (pop) c5 220 m f (min) supply by-pass danger of oscillations c6 100nf (min) supply by-pass danger of oscillations c7 2200 m f output decoupling ch2 - decrease oflow frequency cut off - longer turn on delay - increase of low frequency cut off - shorter turn on delay figure 5: output power vs. supply voltage (stereo) figure 6: output power vs. supply voltage (stereo) figure 8: output power vs. supply voltage (bridge) figure 7: output power vs. supply voltage (stereo) TDA7360 6/22
figure 11: distortion vs output power (stereo) figure 12: distortion vs output power (stereo) figure 9: output power vs. supply voltage (bridge) figure 10: drain current vs supply voltage (stereo) figure 13: distortion vs output power (stereo) figure 14: distortion vs output power (bridge) TDA7360 7/22
figure 15: distortion vs. output power figure 16: svr vs. frequency & c 3 (stereo) figure 17: svr vs. frequency & c 3 (bridge) figure 18: crosstalk vs. frequency (stereo) figure 19: power dissipation & efficiency vs. output power (stereo) figure 20: power dissipation & efficiency vs. output power (stereo) r g r g r g TDA7360 8/22
amplifier organization the TDA7360 has been developed taking care of the key concepts of the modern power audio am- plifier for car radio such as: space and costs sav- ing due to the minimized external count, excellent electrical performances, flexibility in use, superior reliability thanks to a built-in array of protections. as a result the following performances has been achieved: no need of bootstrap capacitors even at the highest output power levels absolute stability without exter- nal compensation thanks to the in- novative out stage configuration, also allowing internally fixed closed loop lower than competi- tors low gain (20db stereo fixed without any external components) in order to minimize the output noise and op- timize svr silent mute/st-by function featur- ing absence of pop on/off noise high svr stereo/bridge operation without addition of external component ac/dc short circuit protection (to gnd, to v s , across the load) loudspeaker protection dump protection esd protection block description polarization the device is organized with the gain resistors di- rectly connected to the signal ground pin i.e. with- out gain capacitors (fig. 23). the non inverting inputs of the amplifiers are con- nected to the svr pin by means of resistor divid- ers, equal to the feedback networks. this allows the outputs to track the svr pin which is suffi- ciently slow to avoid audible turn-on and turn-off transients. svr the voltage ripple on the outputs is equal to the one on svr pin: with appropriate selection of c svr , more than 60db of ripple rejection can be obtained. delayed turn-on (muting) the c svr sets a signal turn-on delay too. a circuit is included which mutes the device until the volt- age on svr pin reaches ~2.5v typ. (fig. 25). the mute function is obtained by duplicating the input differential pair (fig. 24): it can be switched to the signal source or to an internal mute input. this feature is necessary to prevent transients at the inputs reaching the loudspeaker(s) immediately after power-on). fig. 25 represents the detailed turn-on transient with reference to the stereo configuration. at the power-on the output decoupling capacitors are charged through an internal path but the de- vice itself remains switched off (phase 1 of the represented diagram). when the outputs reach the voltage level of about 1v (this means that there is no presence of short circuits) the device switches on, the svr capaci- tor starts charging itself and the output tracks ex- actly the svr pin. during this phase the device is muted until the svr reaches the oplayo threshold (~2.5v typ.), af- ter that the music signal starts being played. figure 22: power dissipation & efficiency vs. output power (bridge) figure 21: power dissipation & efficiency vs. output power (bridge) TDA7360 9/22
stereo/bridge switching there is also no need for external components for changing from stereo to bridge configuration (figg. 23-26). a simple short circuit between two pins al- lows phase reversal at one output, yet maintain- ing the quiescent output voltage. stand-by the device is also equipped with a stand-by func- tion, so that a low current, and hence low cost switch, can be used for turn on/off. stability the device is provided with an internal compen- sation wich allows to reach low values of closed loop gain. in this way better performances on s/n ratio and svr can be obtained. figure 23: block diagram; stereo configuration figure 24: mute function diagram TDA7360 10/22
figure 25: turn-on delay circuit TDA7360 11/22
figure 26: block diagram; bridge configuration clip detector the TDA7360 is equipped with an internal circuit able to detect the output stage saturation provid- ing a proper current sinking into an open collector out. (pin2) when a certain distortion level is reached at each output. this particular function allows compression facility whenever the amplifier is overdriven, so obtaining high quality sound at all listening levels. figure 27: dual channel distortion detector figure 28: output at clipping detector pin vs. signal distortion TDA7360 12/22
output stage poor current capability and low cutoff frequency are well known limits of the standard lateral pnp. composite pnp-npn power output stages have been widely used, regardless their high saturation drop. this drop can be overcome only at the ex- pense of external components, namely, the boot- strap capacitors. the availability of 4a isolated collector pnp (icv pnp) adds versatility to the design. the performance of this component, in terms of gain, v cesat and cut-off frequency, is shown in fig. 29, 30, 31 respectively. it is realized in a new bipolar technology, characterized by top- bottom isolation techniques, allowing the imple- mentation of low leakage diodes, too. it guaran- tees bv ceo > 20v and bv cbo > 50v both for npn and pnp transistors. basically, the connec- tion shown in fig. 32 has been chosen. first of all because its voltage swing is rail-to-rail, limited only by the vcesat of the output transistors, which are in the range of 0.3 w each. then, the gain vout/vin is greater than unity, approxi- mately 1+r2/r1. (vcc/2 is fixed by an auxiliary amplifier common to both channel). it is possible, controlling the amount of this local feedback, to force the loop gain (a * b ) to less than unity at fre- quencies for which the phase shift is 180 . this means that the output buffer is intrinsically stable and not prone to oscillation. in contrast, with the circuit of fig. 33, the solution adopted to reduce the gain at high frequencies is the use of an external rc network. amplifier block diagram the block diagram of each voltage amplifier is shown in fig. 34. regardless of production spread, the current in each final stage is kept low, with enough margin on the minimum, below which cross-over distortion would appear. figure 29: icv - pnp gain vs. i c figure 30: icv - pnp v ce(sat ) vs. i c figure 31: icv - pnp cut-off frequency vs. i c figure 32: the new output stage TDA7360 13/22
built-in protection systems short circuit protection the maximum current the device can deliver can be calculated by considering the voltage that may be present at the terminals of a car radio amplifier and the minimum load impedance. apart from consideration concerning the area of the power transistors it is not difficult to achieve peak currents of this magnitude (5 a peak). however, it becomes more complicated if ac and dc short circuit protection is also required.in par- ticular, with a protection circuit which limits the output current following the soa curve of the out- put transistors it is possible that in some condi- tions (highly reactive loads, for example) the pro- tection circuit may intervene during normal operation. for this reason each amplifier has been equipped with a protection circuit that inter- venes when the output current exceeds 4a fig 35 shows the protection circuit for an npn power transistor (a symmetrical circuit applies to pnp).the vbe of the power is monitored and gives out a signal,available through a cascode. this cascode is used to avoid the intervention of the short circuit protection when the saturation is below a given limit. the signal sets a flip-flop which forces the amplifier outputs into a high impedance state. in case of dc short circuit when the short circuit is removed the flip-flop is reset and restarts the circuit (fig. 39). in case of ac short circuit or load shorted in bridge configuration, the device is con- tinuously switched in on/off conditions and the current is limited. figure 34: amplifier block diagram figure 33: a classical output stage figure 35: circuitry for short circuit detection TDA7360 14/22
load dump voltage surge the tda 7360 has a circuit which enables it to withstand a voltage pulse train on pin 9, of the type shown in fig. 37. if the supply voltage peaks to more than 50v, then an lc filter must be inserted between the supply and pin 9, in order to assure that the pulses at pin 9 will be held within the limits shown. a suggestedlc network is shown in fig. 36. with this network, a train of pulses with amplitude up to 120v and width of 2ms can be applied at point a. this type of protection is on when the supplyvoltage (pulse or dc) exceeds 18v. for this reason the maxi- mum operating supply voltage is 18v. polarity inversion high current (up to 10a) can be handled by the de- vice with no damage for a longer period than the blow-out time of a quick 2a fuse (normally connected in series with the supply). this features is added to avoid destruction, if during fitting to the car, a mistake on the connection of the supply is made. open ground when the radio is in the on condition and the ground is accidentally opened, a standard audio amplifier will be damaged. on the TDA7360 pro- tection diodes are included to avoid any damage. dc voltage the maximum operating dc voltage for the TDA7360 is 18v. however the device can withstand a dc voltage up to 28v with no damage. this could occur dur- ing winter if two batteries are series connected to crank the engine. thermal shut-down the presence of a thermal limiting circuit offers the following advantages: 1)an overload on the output (even if it is perma- nent), or an excessive ambient temperature can be easily withstood. 2)the heatsink can have a smaller factor of safety compared with that of a conventional circuit. there is no device damage in the case of ex- cessive junction temperature: all happens is that p o (and therefore p tot ) and i d are reduced. the maximum allowable power dissipation de- pends upon the size of the external heatsink (i.e. its thermal resistance); fig. 38 shows the dissi- pable power as a function of ambient temperature for different thermal resistance. loudspeaker protection the TDA7360 guarantees safe operations even for the loudspeaker in case of accidental shortcir- cuit. whenever a single out to gnd, out to v s short circuit occurs both the outputs are switched off so limiting dangerous dc current flowing through the loudspeaker. figure 36 figure 37 figure 38: maximum allowable power dissipation vs. ambient temperature figure 39: restart circuit TDA7360 15/22
application hints this section explains briefly how to get the best from the TDA7360 and presents some application circuits with suggestions for the value of the com- ponents.these values can change depending on the characteristics that the designer of the car ra- dio wants to obtain,or other parts of the car radio that are connected to the audio block. to optimize the performance of the audio part it is useful (or indispensable) to analyze also the parts outside this block that can have an interconnec- tion with the amplifier. this method can provide components and system cost saving. reducing turn on-off pop the TDA7360 has been designed in a way that the turn on(off) transients are controlled through the charge(discharge) of the csvr capacitor. as a result of it, the turn on(off) transient spec- trum contents is limited only to the subsonic range.the following section gives some brief notes to get the best from this design feature(it will refer mainly to the stereo application which appears to be in most cases the more critical from the pop viewpoint.the bridge connection in fact,due to the common mode waveform at the outputs,does not give pop effect). turn-on fig 40 shows the output waveform (before and after the oao weighting filter) compared to the value of csvr. better pop-on performance is obtained with higher csvr values (the recommended range is from 22uf to 220uf). the turn-on delay (during which the amplifier is in mute condition) is a function essentially of : c out , c svr . being: t1 120 ? c out t2 1200 ? c svr the turn-on delay is given by: t1+t2 stereo t2 bridge the best performance is obtained by driving the st-by pin with a ramp having a slope slower than 2v/ms figure 40: a) c svr =22 m f b) c svr =47 m f c) c svr = 100 m f TDA7360 16/22
turn-off a turn-off pop can occur if the st-by pin goes low with a short time constant (this can occur if other car radio sections, preamplifiers,radio.. are sup- plied through the same st-by switch). this pop is due to the fast switch-off of the inter- nal current generator of the amplifier. if the voltage present across the load becomes rapidly zero (due to the fast switch off) a small pop occurs, depending also on cout,rload. the parameters that set the switch off time con- stant of the st-by pin are: ? the st-by capacitor (cst-by) ? the svr capacitor (csvr) ? resistors connected from st-by pin to ground (rext) the time constant is given by : t csvr ? 2000 w // rext + cst-by ? 2500 w // rext the suggested time constants are : t > 120ms with c out =1000 m f,r l = 4ohm,stereo t > 170ms with c out =2200 m f,r l = 4ohm,stereo if rext is too low the csvr can become too high and a different approach may be useful (see next section). figg 41, 42 show some types of electronic switches ( m p compatible) suitable for supplying the st-by pin (it is important that qsw is able to saturate with v ce 150mv). also for turn off pop the bridge configuration is su- perior, in particular the st-by pin can go low faster. global approach to solving pop problem by using the muting/turn on delay function in the real case turn-on and turn-off pop problems are generated not only by the power amplifier,but also (very often) by preamplifiers,tone controls,ra- dios etc. and transmitted by the power amplifier to the loudspeaker. a simple approach to solving these problems is to use the mute characteristics of the TDA7360. if the svr pin is at a voltage below 1.5 v, the mute attenuation (typ) is 30db .the amplifier is in play mode when vsvr overcomes 3.5 v. with the circuit of fig 43 we can mute the amplifier for a time ton after switch-on and for a time toff after switch-off.during this period the circuitry that precedes the power amplifier can produce spuri- ous spikes that are not transmitted to the loud- speaker. this can give back a very simple design of this circuitry from the pop point of view. a timing diagram of this circuit is illustrated in fig 44. other advantages of this circuit are: - a reduced time constant allowance of stand-by pin turn off.consequently it is possible to drive all the car-radio with the signal that drives this pin. -a better turn-off noise with signal on the output. to drive two stereo amplifiers with this circuit it is possible to use the circuit of fig 45. figure 41 figure 42 TDA7360 17/22
figure 43 figure 44 TDA7360 18/22
balanced input in bridge configuration a helpful characteristic of the TDA7360 is that,in bridge configuration, a signal present on both the input capacitors is amplified by the same amount and it is present in phase at the outputs,so this signal does not produce effects on the load.the typical value of cmrr is 46 db. looking at fig 46, we can see that a noise signal from the ground of the power amplifier to the ground of the hypothetical preamplifier is ampli- fied of a factor equal to the gain of the amplifier (2 * gv). using a configuration of fig. 47 the same ground noise is present at the output multiplied by the factor 2 * gv/200. this means less distortion,less noise (e.g. motor cassette noise ) and/or a simplification of the lay- out of pc board. the only limitation of this balanced input is the maximum amplitude of common mode signals (few tens of millivolt) to avoid a loss of output power due to the common mode signal on the output, but in a large number of cases this signal is within this range. figure 46 figure 47 figure 45 TDA7360 19/22
multiwatt11 v dim. mm inch min. typ. max. min. typ. max. a5 0.197 b 2.65 0.104 c 1.6 0.063 d 1 0.039 e 0.49 0.55 0.019 0.022 f 0.88 0.95 0.035 0.037 g 1.45 1.7 1.95 0.057 0.067 0.077 g1 16.75 17 17.25 0.659 0.669 0.679 h1 19.6 0.772 h2 20.2 0.795 l 21.9 22.2 22.5 0.862 0.874 0.886 l1 21.7 22.1 22.5 0.854 0.87 0.886 l2 17.4 18.1 0.685 0.713 l3 17.25 17.5 17.75 0.679 0.689 0.699 l4 10.3 10.7 10.9 0.406 0.421 0.429 l7 2.65 2.9 0.104 0.114 m 4.25 4.55 4.85 0.167 0.179 0.191 m1 4.73 5.08 5.43 0.186 0.200 0.214 s 1.9 2.6 0.075 0.102 s1 1.9 2.6 0.075 0.102 dia1 3.65 3.85 0.144 0.152 outline and mechanical data TDA7360 20/22
dim. mm inch min. typ. max. min. typ. max. a 4.373 4.5 4.627 0.172 0.177 0.182 b 2.65 0.104 c 1.6 0.063 e 0.49 0.515 0.55 0.019 0.020 0.022 e1 1.007 1.037 1.07 0.040 0.041 0.042 f 0.88 0.9 0.95 0.035 0.035 0.037 g 1.5 1.7 1.9 0.059 0.067 0.075 g.1 16.82 17.02 17.22 0.662 0.670 0.678 g2 6.61 6.807 7.01 0.260 0.268 0.276 g3 13.41 13.61 13.81 0.528 0.536 13.810 g4 3.2 3.4 3.6 0.126 0.134 0.142 g5 10.01 10.21 10.41 0.394 0.402 0.410 h1 19.6 0.77 2 h2 20.2 0.795 l1 19.28 19.58 19.88 0.759 0.771 0.783 l2 3.61 3.81 4.01 0.142 0.150 0.158 l3 17.25 17.5 17.75 0.679 0.689 0.699 l4 10.3 10.6 10.9 0.406 0.417 0.429 l5 (inner) 3.4 3.75 4 0.134 0.148 0.157 l5 (outer) 3.6 3.9 4.2 0.142 0.154 4.200 l7 2.65 2.9 0.104 0.114 r 0.75 1 1.25 0.030 0.039 0.049 s 1.9 2.6 0.075 0.102 s1 1.9 2.6 0.075 0.102 dia1 3.65 3.85 0.144 0.152 multiwatt11 h (short leads) l7 h1 dia.1 s s1 l3 l4 p l1 v e h2 g3 c a b l5 mult11lhm n g g2 f rr vv l2 v x g4 g5 g1 h2 0.25min 0.50max detail x 60 to 90 e1 f e r1 outline and mechanical data TDA7360 21/22
information furnished is believed to be accurate and reliable. however, stmicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of stmicroelectronics. specification mentioned in this publication are subject to change without notice. this publication supersedes and replaces all information previously supplied. stmicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of stmicroelectronics. the st logo is a registered trademark of stmicroelectronics multiwatt ? is a registered trademark of the stmicroelectronics ? 1998 stmicroelectronics printed in italy all rights reserved stmicroelectronics group of companies australia - brazil - canada - china - france - germany - italy - japan - korea - malaysia - malta - mexico - morocco - the netherlands - singapore - spain - sweden - switzerland - taiwan - thailand - united kingdom - u.s.a. http://www.st.com TDA7360 22/22

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